AC LED dimmer and dimming method thereby

ABSTRACT

The disclosure relates to an AC LED dimmer and dimming method thereof. The AC LED dimmer includes a rectifier receiving AC voltage from an AC voltage source and full-wave rectifying the AC voltage; a direct current (DC)/DC converter receiving the full-wave rectified voltage from the rectifier, generating a full-wave rectified stepped-up voltage, and generating a pulse enable signal; a pulse width modulation controller receiving the full-wave rectified stepped-up voltage and generating a pulse width modulation signal to dim an AC LED in response to the pulse enable signal; a switch driving the AC LED under control of the pulse width modulation signal, and an electromagnetic interference (EMI) filter to be connected between the AC voltage source and the switch to eliminate electromagnetic interference from the AC voltage source. Accordingly, the dimmer can perform an efficient and linear dimming function and suppress harmonics.

CROSS REFERENCE TO RELATED APPLICATION

This application claims priority from and the benefit of Korean PatentApplication No. 10-2008-0087758, filed on Sep. 5, 2008, which is herebyincorporated by reference for all purposes as if fully set forth herein.

BACKGROUND OF THE INVENTION

1. Field of the Invention

Exemplary embodiments of the present invention relate to an alternatingcurrent (AC) light-emitting diode (LED) dimmer and a dimming methodthereby and, more particularly, to an AC LED dimmer which performs adimming function of an AC LED by bidirectionally switching AC voltage ata high speed under control of a pulse width modulation signal, and adimming method thereby.

2. Discussion of the Background

In general, a lamp may have a dimming function that allows a user tocontrol brightness of the lamp, but such a function has beenrestrictively used in practice. As energy saving has become an importantconcern in association with an increase in electrical energyconsumption, the dimming function of the lamp becomes an essentialfunction, rather than an optional function, to save energy. Further, alight-emitting diode (LED) has attracted attention as an environmentallyfriendly lighting source to save electric energy.

A conventional representative dimmer dims an AC LED by adjusting theroot-mean-square (RMS) value (Vrms) of AC voltage by controlling the ACphase of the AC voltage using a semiconductor device such as a triodefor alternating current (Triac).

A Triac is an electronic component approximately equivalent to twosilicon-controlled rectifiers (SCRs/thyristors) connected to each otherin inverse parallel (parallel but with the polarity reversed) and withtheir gates connected together. The Triac can be triggered by either apositive or a negative voltage applied to its gate electrode, and, oncetriggered, it continues to conduct until the current through the Triacdrops below a certain threshold value. Triacs are well known in the artand a detailed description thereof will be omitted herein.

Such a phase control scheme adjusts the RMS value of output voltage bydriving the Triac after a predetermined delay from when an input voltageis 0V (at the moment when the input voltage starts to rise or decrease).However, the phase control scheme and the traditional dimming methodusing the Triac are limited in terms of operating range due to acontroller configured to drive the Triac and inherent characteristics ofthe Triac.

The traditional dimmer and dimming method will be described withreference to the accompanying drawings.

FIG. 1 is a block diagram of a traditional dimmer using a Triac. Thedimmer 10 includes a Triac 14 and a resistor/capacitor (R/C) phasecontroller 16. The Triac 14 supplies or blocks AC voltage from an ACvoltage source 12 to a lamp, i.e. an AC LED 18, and the R/C phasecontroller 16 controls the Triac 14. Hence, the Triac 14 is turned on bya gate turn-on signal g from the R/C phase controller 16 to allow the ACvoltage to be supplied to the AC LED 18.

The dimmer 10 generates a phase control signal, i.e., gate turn-onsignal I_(G), using a resistor R and a capacitor C, when the AC inputvoltage is 0V, to drive the Triac 14. The phase control signal is an ACvoltage signal delayed by a time constant determined by the resistor andthe capacitor.

Considering the operating characteristics of a typical Triac, thedimming range of the dimmer 10 is limited depending on the drive voltageof the Triac.

FIG. 2 is a waveform graph of AC input voltage v₁ and AC input currenti₁ in the traditional dimmer in FIG. 1. Referring to FIG. 2, the phasecontrol scheme using the Triac leads to a non-sinusoidal waveform of thecurrent i₁.

When the AC input voltage is 0V, a phase control signal, i.e., gateturn-on signal I_(G) in FIG. 1, which is generated using the resistor Rand the capacitor C, causes the Triac 14 (see FIG. 1) to abruptlyconduct current due to the operation characteristics of the Triac,thereby resulting in the non-sinusoidal waveform of the current i₁, asshown in FIG. 2. Further, a time point when the current i₁ starts toflow in the current waveform depends on the resistor and the capacitorof the R/C phase controller 16. In determining such a phase delay, anoperating margin of the resistor and the capacitor is required. Aninsufficient operating margin may cause the gate turn-on signal I_(G)(see FIG. 1) to instantaneously flow, thereby causing the AC LED toflicker.

As such, there is a problem in that a minimum dimming range and amaximum dimming range are very limited due to the drive voltage of theTriac and the characteristics of the resistor and capacitor of the R/Cphase controller.

In addition, the Triac is abruptly switched by the gate turn-on signalin the phase control scheme using the Triac, thereby producing a numberof harmonics during the switching process (especially, turn-on timedenoted by reference numeral 20 in FIG. 2).

Accordingly, a new AC voltage source driver and controller are needed toachieve a broader control range and a linear dimming function.

SUMMARY OF THE INVENTION

Exemplary embodiments of the present invention provide an improved ACLED dimmer and dimming method capable of addressing the problem of theconventional dimmer in which the dimming range is limited by the drivevoltage of the Triac and the characteristics of the resistor andcapacitor of the R/C phase controller.

Exemplary embodiments of the present invention also provide an improvedAC LED dimmer and dimming method capable of addressing the problem ofthe conventional dimmer in which a number of harmonics are produced inthe turn-on switching operation.

Exemplary embodiments of the present invention also provide an improvedAC LED dimmer and dimming method capable of reducing or minimizingflickering of the AC LED caused by the insufficient operating margin ofthe resistor and capacitor of the R/C phase controller in theconventional dimmer.

Additional features of the invention will be set forth in thedescription which follows, and in part will be apparent from thedescription, or may be learned by practice of the invention.

An exemplary embodiment of the present invention discloses analternating current (AC) light-emitting diode (LED) dimmer that includesa rectifier to receive AC voltage from an AC voltage source and to firstfull-wave rectify the AC voltage. A voltage converter is included in thedimmer to receive the first full-wave rectified voltage from therectifier, to generate a second full-wave rectified stepped-up voltage,and to generate a pulse enable signal. The dimmer also includes a pulsewidth modulation controller to receive the second full-wave rectifiedstepped-up voltage and to generate a pulse width modulation signal todim an AC LED in response to the pulse enable signal; and a switch todrive the AC LED under control of the pulse width modulation signal.

An exemplary embodiment of the present invention also discloses an ACLED dimming method that includes receiving AC voltage and generating apulse width modulation signal. The method includes driving an AC LEDunder control of the pulse width modulation signal; and dimming the ACLED by adjusting a duty cycle of the pulse width modulation signal.

An exemplary embodiment of the present invention also discloses an ACLED dimming method that includes receiving and first full-waverectifying AC voltage to generate first full rectified voltage. Themethod includes generating second full-wave rectified stepped-up voltagefrom the first full-wave rectified voltage, and generating a pulseenable signal. The method includes generating a pulse width modulationsignal from the second full-wave rectified stepped-up voltage and inresponse to the pulse enable signal. The method also includes switchingbidirectionally according to the AC voltage under control of the pulsewidth modulation signal to drive an AC LED; and dimming the AC LED byadjusting a duty cycle of the pulse width modulation signal.

It is to be understood that both the foregoing general description andthe following detailed description are exemplary and explanatory and areintended to provide further explanation of the invention as claimed.

BRIEF DESCRIPTION OF THE DRAWINGS

The accompanying drawings, which are included to provide a furtherunderstanding of the invention and are incorporated in and constitute apart of this specification, illustrate embodiments of the invention, andtogether with the description serve to explain the principles of theinvention.

FIG. 1 is a block diagram of a traditional dimmer using a Triac.

FIG. 2 is a waveform graph of AC input voltage and current in the dimmerin FIG. 1.

FIG. 3 is a block diagram of an AC LED dimmer according to an exemplaryembodiment of the present invention.

FIG. 4 is a waveform graph of AC input voltage and current in the AC LEDdimmer in FIG. 3.

FIG. 5A and FIG. 5B are circuit diagrams of exemplary embodiments of anelectromagnetic interference filter in FIG. 3.

FIG. 6 is a circuit diagram of an exemplary embodiment of a rectifier inFIG. 3.

FIG. 7 is a circuit diagram of an exemplary embodiment of a voltageconverter in FIG. 3.

FIG. 8 is a circuit diagram of an exemplary embodiment of a pulse widthmodulation controller in FIG. 3.

FIG. 9A is a waveform when a pulse width modulation signal V_(PWM)indicates a minimum output.

FIG. 9B is a waveform when a pulse width modulation signal V_(PWM) has aduty cycle of 70%.

FIG. 9C is a waveform when a pulse width modulation signal V_(PWM) has aduty cycle of 100%.

FIG. 10 is a circuit diagram of an exemplary embodiment of a switch inFIG. 3.

FIG. 11A, FIG. 11B and FIG. 11C are waveforms illustrating the relationbetween input voltage and input current of an AC LED according to dutycycles of a pulse width modulation signal V_(PWM) in an AC LED dimmeraccording to an exemplary embodiment of the present invention.

DETAILED DESCRIPTION OF THE ILLUSTRATED EMBODIMENTS

The invention is described more fully hereinafter with reference to theaccompanying drawings, in which embodiments of the invention are shown.This invention may, however, be embodied in many different forms andshould not be construed as limited to the embodiments set forth herein.Rather, these embodiments are provided so that this disclosure isthorough, and will fully convey the scope of the invention to thoseskilled in the art. In the drawings, the size and relative sizes oflayers and regions may be exaggerated for clarity. Like referencenumerals in the drawings denote like elements.

It will be understood that when an element or layer is referred to asbeing “on” or “connected to” another element or layer, it can bedirectly on or directly connected to the other element or layer, orintervening elements or layers may be present. In contrast, when anelement or layer is referred to as being “directly on” or “directlyconnected to” another element or layer, there are no interveningelements or layers present. Likewise, when an element is referred to asbeing “connected between” other elements, it can be directly connectedto each of the other elements or intervening elements may be present. Incontrast, when an element is referred to as being “directly connectedbetween” other elements, there are no intervening elements present.

FIG. 3 is a block diagram of an alternating current (AC) light-emittingdiode (LED) dimmer according to an exemplary embodiment of the presentinvention.

The AC LED dimmer 100 includes an electromagnetic interference (EMI)filter 102, an alternating current to direct current (AC/DC) rectifier104, a voltage converter 106, a pulse width modulation (PWM) controller108 and a switch 110.

The EMI filter 102 is connected between an AC voltage source 120 and theswitch 110 and acts to eliminate electromagnetic interference includedin the AC voltage source 120. That is, the EMI filter 102 eliminates animpulse noise, harmonics or the like due to electromagnetic interferenceinside or outside the dimmer 100 which is produced in a power linebetween the AC voltage source 120 and an AC LED 180. The EMI filter 102may be optional, but is preferably included to reduce theelectromagnetic interference and improve a power factor. The AC/DCrectifier 104 receives an AC voltage from the AC voltage source 120 andfull-wave rectifies it into a direct current (DC) voltage V_(dc1). TheEMI filter 102 allows the AC/DC rectifier 104 to receive a voltagev_(out) having reduced electromagnetic interference. The voltageconverter 106 receives a voltage V_(dc1) which is full-wave rectified bythe AC/DC rectifier 104, and outputs a voltage V_(dc2), which isfull-wave rectified and stepped up, and a pulse enable signal P_(en)_(—) _(PWM). That is, the voltage converter 106 outputs the DC voltageV_(dc2), which is isolated from the AC voltage source 120, and alsooutputs the pulse enable signal P_(en) _(—) _(PWM) to be used ingenerating a pulse width modulation signal V_(PWM).

The PWM controller 108 receives the voltage V_(dc2) from the voltageconverter 106 and generates a pulse width modulation signal V_(PWM) inresponse to the pulse enable signal P_(en) _(—) _(PWM).

The switch 110 drives the AC LED 180 under the control of the pulsewidth modulation signal V_(PWM). If the EMI filter 102 is employed, theswitch 110 receives the voltage v_(out) having reduced electromagneticinterference and drives the AC LED 180.

Accordingly, the AC LED dimmer 100 including the above-mentionedelements can solve the problems of the conventional dimmer employing theTriac, i.e., a limited dimming range due to the drive voltage of theTriac and the characteristics of the resistor and capacitor of the R/Cphase controller, harmonics produced in the turn-on switching operation,and flickering of the AC LED due to an insufficient margin of theresistor and capacitor of the R/C phase controller.

FIG. 4 is a waveform graph illustrating AC input voltage v₄ and currenti₄ when the AC LED dimmer in FIG. 3 is employed. The term input voltagerefers to an input voltage to the AC LED 180. The graph of the inputvoltage and current illustrates a pulse width modulation signal V_(PWM)having a duty cycle of 100%.

Comparing FIG. 4 with FIG. 2, although voltage waveforms v₁ and v₄ aresimilar (AC voltage source is assumed to be identical), the currentwaveform i₄ in FIG. 4 is closer to sinusoidal. Further, it is possibleto suppress harmonics that may be produced when the Triac is abruptlyturned on as in the current waveform i₁ in FIG. 2.

FIG. 5A and FIG. 5B are exemplary embodiments of circuit diagramsillustrating the EMI filter 102 in FIG. 3. Referring to FIG. 5A, the EMIfilter 102 is a line filter (also referred to as an AC line filter)including a filter capacitor C₁ and common mode inductors L₁ and L₂. Theline filter is an LC low pass filter which may reduce electromagneticinterference included in a voltage source. The AC voltage v_(out) is avoltage having reduced electromagnetic interference.

The EMI filter 102 may be designed such that the filter capacitor C₁ hasa low capacitance and the common mode inductors L₁ and L₂ have a largeinductance to enhance the power factor.

The common mode inductors L₁ and L₂ formed of a single stage as shown inFIG. 5A may be physically limited by number of windings, size and thelike. In order to overcome such physical limitations and increaseinductance of the common mode inductors to thereby increase the powerfactor, the common mode inductors may be formed of two or more stageswhich are connected to each other in series.

FIG. 5B illustrates two stages of common mode inductors L₃ and L₄ and L₅and L₆ which are connected in series to each other. FIG. 5B is providedonly for illustrative purposes and the common mode inductors may beformed of three or more stages.

Accordingly, by using the EMI filter 102, it is possible to produce anearly sinusoidal input current to the AC LED 180, to suppress harmonicsand to reduce electromagnetic interference.

FIG. 6 is a circuit diagram illustrating an exemplary embodiment of theAC/DC rectifier 104 in FIG. 3. The AC/DC rectifier 104 includes avoltage divider 114 to divide voltage of an AC voltage source v_(in), afirst full-wave rectifying unit 124 to full-wave rectify the voltagedivided by the voltage divider 114, and a first voltage stabilizerhaving a capacitor C₆₂ to stabilize the voltage full-wave rectified bythe first full-wave rectifying unit 124.

Here, the AC voltage source v_(in) may be an AC voltage source 120 withno electromagnetic interference filtered or, if the EMI filter 102 isused, an AC voltage source (v_(out) in FIG. 5A or FIG. 5 b) withelectromagnetic interference filtered.

The voltage divider 114 includes a capacitor C₆₁ which is connected inseries to the AC voltage source v_(in), a resistor R₆₁, which isconnected in series to the capacitor C₆₁, and a pair of Zener diodesZD₆₁ and ZD₆₂ which are connected in series to the resistor R₆₁. Apredetermined Zener voltage V_(ZD) across the Zener diodes ZD₆₁ and ZD₆₂is connected in parallel to an input of the first full-wave rectifyingunit 124.

The pair of Zener diodes ZD₆₁ and ZD₆₂ are connected in inverse seriesto provide predetermined Zener voltages V_(ZD) and −V_(ZD) under the ACvoltage source v_(in).

An operation of the AC/DC rectifier 104 will now be described in detail.

Since the capacitor C₆₁, the resistor R₆₁ and the pair of Zener diodesZD₆₁ and ZD₆₂ are connected in series to the AC voltage source v_(in)and the pair of Zener diodes ZD₆₁ and ZD₆₂ are connected to an input ofthe first full-wave rectifying unit 124, the pair of Zener diodes ZD₆₁and ZD₆₂ act to limit an input voltage of the first full-wave rectifyingunit 124 to a predetermined Zener voltage V_(ZD).

The voltage across the capacitor C₆₁ may vary depending on powerconsumption of the capacitor C₆₂ of the first voltage stabilizer. Inthis case, for the capacitor C₆₁, the resistor R₆₁ and the pair of Zenerdiodes ZD₆₁ and ZD₆₂, which are connected in series to each other, thevoltage of the AC voltage source v_(in) is divided in a predeterminedproportion, and the AC input voltage of the first full-wave rectifyingunit 124 including diodes D₆₁, D₆₂, D₆₃ and D₆₄ varies depending on thepower consumption of the capacitor C₆₂.

Hence, the capacitance of the capacitor C₆₁ may be designed inconsideration of the power consumption of the capacitor C₆₂. Forexample, the capacitor C₆₁ may have a capacitance of 100 to 330 nF.

Further, the pair of Zener diodes ZD₆₁ and ZD₆₂ may be optionalaccording to whether the capacitor C₆₁ may be optimally designed takinginto account the power consumption of the capacitor C₆₂.

The capacitor C₆₂ forms the first voltage stabilizer. The first voltagestabilizer stabilizes the voltage rectified by the first full-waverectifying unit 124 into DC voltage and provides it to the voltageconverter 106.

FIG. 7 is a circuit diagram illustrating an exemplary embodiment of thevoltage converter 106 in FIG. 3, i.e., a DC/DC voltage converter. Thevoltage converter 106 includes a pulse generator 116, a first amplifier146, a transformer TR₇₁, a second full-wave rectifying unit 166, and asecond voltage stabilizer 156. The pulse generator 116 receives theoutput voltage V_(dc1) of the AC/DC rectifier 104 and generates ahigh-frequency pulse signal P₁. The first amplifier 146 receives thehigh-frequency pulse signal P₁ and outputs an AC square wave signal P₂.The transformer TR₇₁ receives the AC square wave signal P₂ in itsprimary winding and induces a stepped-up voltage in its secondarywinding. The second full-wave rectifying unit 166 full-wave rectifiesthe voltage v₂ induced in the secondary winding of the transformer TR₇₁and outputs a pulse enable signal P_(en) _(—) _(PWM) to be applied tothe PWM controller 108. The second voltage stabilizer 156 stabilizes thevoltage (voltage at N₇₃) full-wave rectified by the second full-waverectifying unit 166.

The pulse generator 116 is an oscillator to generate a square wave andincludes a duty cycle adjustor 126 and a timer integrated circuit (IC)136. Although the exemplary embodiment of the timer IC 136 of the pulsegenerator 116 is an NE555 timer IC in FIG. 7, the timer IC 136 may beany IC which may generate a high-frequency pulse signal.

For example, for the timer IC 136, a GND pin (pin 1) is connected to aground; a THR (pin 2), TRG (pin 6) and DIS (pin 7) are connected to aperipheral circuit 126 for adjusting a duty cycle (referred to as“duty-cycle adjustor”); a VCC (pin 4) and RST (pin 8) are connected toDC voltage V_(dc1); and a CV (pin 5) is connected to a capacitor C₇₃ tostabilize the timer IC 136.

The duty-cycle adjustor 126 includes a first resistor R₇₁, a secondresistor R₇₂ and a capacitor C₇₂, which are connected in series to eachother, where DC voltage V_(dc1) is applied.

Pin 7 of the timer IC 136 is connected to a node N₇₁ between the firstresistor R₇, and the second resistor R₇₂; pins 2 and 6 of the timer IC136 are commonly connected to a node N₇₂ between the second resistor R₇₂and the capacitor C₇₂. As such, a duty cycle is determined by theoperation of the timer IC 136 and a time constant determined by thefirst resistors R₇₁, the second resistor R₇₂, and the capacitor C₇₂.

As shown in FIG. 7, to generate a high-frequency pulse signal P₁ with aduty cycle of 50%, a diode D₇₁ may be further included which isconnected in parallel to the second resistor R₇₂ and is forward biasedtoward the capacitor C₇₂.

The first amplifier 146 receives the high-frequency pulse signal P₁ andapplies the AC square wave signal P₂ to the primary winding of thetransformer TR₇₁.

For example, as shown in FIG. 7, the first amplifier 146 may include apair of bipolar junction transistors (BJTs) Q₇₁ and Q₇₂. The BJT Q₇₁ isan NPN transistor and the BJT Q₇₂ is a PNP transistor. Bases of the BJTsQ₇₁ and Q₇₂ are commonly connected to an output of the pulse generator116; their emitters are commonly connected to each other; and theircollectors are connected to an output of the AC/DC rectifier 104. Thatis, the collector of the BJT Q₇₁ is connected to the DC voltage sourceV_(dc1) and the collector of the BJT Q₇₂ is connected to the ground, sothat they are driven by the DC voltage source V_(dc1).

The emitters of the BJTs Q₇₁ and Q₇₂ are commonly connected to theprimary winding of the transformer TR₇₁ so that the AC square wavesignal P₂ is output from the emitters to the transformer TR₇₁.

A DC cutoff capacitor C₇₄ may be further connected in series between thecommon emitters of the BJTs Q₇₁ and Q₇₂ and the primary winding of thetransformer TR₇₁ to block the DC signal.

The second full-wave rectifying unit 166 includes four diodes D₇₂, D₇₃,D₇₄ and D₇₅. The second full-wave rectifying unit 166 is connected tothe secondary winding of the transformer TR₇₁ to full-wave rectify thevoltage stepped up by the transformer TR₇₁ (i.e., the voltage v₂ in thesecondary winding of the transformer TR₇₁). The capacitor C₇₅ isconnected in parallel to the output of the second full-wave rectifyingunit 166 to stabilize the DC voltage.

The second voltage stabilizer 156 includes a BJT Q₇₃, a resistor R₇₃, aZener diode ZD₇₁ and a capacitor C₇₆, for example.

The BJT Q₇₃ illustrated in FIG. 7 is an NPN transistor, a collector ofwhich is connected to the output of the second full-wave rectifying unit166; an emitter of which is connected to the input of the PWM controller108; a collector of which is connected to the Zener diode ZD₇₁. Theresistor R₇₃ with a predetermined resistance is connected between thecollector and base of the BJT Q₇₃, and the Zener diode ZD₇₁ is connectedbetween the base of the BJT Q₇₃ and the output ground node N₇₄ of thevoltage converter 106 to supply a predetermined Zener voltage to thebase of the BJT Q₇₃. The capacitor C₇₆ is connected in parallel to theoutput of the voltage converter 106 to stabilize the DC voltage V_(dc2).

Although the second voltage stabilizer 156 is the BJT Q₇₃, especiallythe NPN BJT, in FIG. 7, it may be a PNP BJT (it should be understoodthat the other elements would need to be differently designedaccordingly) or other circuits capable of stabilizing the DC voltageV_(dc2).

A noise filter 176 may be added between the ground node N₇₅ in theprimary winding of the transformer TR₇₁ and the output ground node N₇₄of the voltage converter 106. The noise filter 176 may generate a stableDC voltage V_(dc2) by stabilizing the ground node N₇₄ in the secondarywinding of the transformer TR₇₁, i.e., the ground at the output of thevoltage converter 106, and passing a noise in a circuit connected to thesecondary winding of the transformer TR₇₁ to the primary winding of thetransformer TR₇₁.

The noise filter 176 may include a combination of a capacitor, aresistor and the like, or a resistor having a resistance of hundreds ofkilo-ohms (kΩ) to thousands of kΩ.

An operation of the voltage converter 106 will be described withreference to FIG. 7. The output voltage V_(dc1) of the AC/DC rectifier104 is charged or stabilized by the capacitor C₇₁, and the timer IC 136and the transistors Q₇₁ and Q₇₂ of the first amplifier 146 are driven bythe DC voltage V_(dc1) across the capacitor C₇₁.

The timer IC 136 generates a high-frequency pulse signal P₁ with apredetermined duty cycle which depends on a time constant determined bythe first resistor R₇₁, the second resistor R₇₂, and the capacitor C₇₂.The first amplifier 146 amplifies the current using the high-frequencypulse signal P₁ and provides an AC square wave signal P₂ to the primarywinding of the transformer TR₇₁ through the DC cutoff capacitor C₇₄. Thevoltage in the primary winding of the transformer TR₇₁ is stepped up ata predetermined ratio in the secondary winding of the transformer TR₇₁.The stepped-up voltage v₂ is full-wave rectified by the second full-waverectifying unit 166 including the diodes D₇₂, D₇₃, D₇₄ and D₇₅. Thefull-wave rectified voltage is stabilized to the DC voltage (voltage atN₇₃) by the capacitor C₇₅. The DC voltage is further stabilized to DCvoltage V_(dc2) by the second voltage stabilizer 156 and the DC voltageV_(dc2) is applied to the PWM controller 108. Further, the pulse enablesignal P_(en) _(—) _(PWM) which is output from a node between the diodesD₇₅ and D₇₄ of the second full-wave rectifying unit 166 is provided tothe PWM controller 108 to generate the pulse width modulation signalV_(PWM).

The voltage converter 106 may allow the primary winding of thetransformer TR₇₁ to generate AC voltage and may allow the secondarywinding of the transformer TR₇₁, which is electrically isolated from theprimary winding, to step up the voltage generated in the primary windingand generate the stable DC voltage V_(dc2).

FIG. 8 is a circuit diagram of an exemplary embodiment of the pulsewidth modulation (PWM) controller 108 in FIG. 3. The PWM controller 108includes a duty-cycle control unit 128 including variable resistorR_(var), constant resistor R₈₃ and capacitor C₈₂, a square wave pulsegenerator 118, and a second amplifier 138 including BJTs Q₈₁ and Q₈₂.The output DC voltage V_(dc2) of the voltage converter 106 is charged orstabilized by the capacitor C₈₁.

The duty-cycle control unit 128 determines a shift time of the PWMsignal V_(PWM) generated by the pulse enable signal P_(en) _(—) _(PWM)by a time constant that is a function of the variable resistor R_(var),the constant resistor R₈₃ and the capacitor C₈₂.

The square wave pulse generator 118 receives the pulse enable signalP_(en) _(—) _(PWM) to shift a square wave pulse P₃ to a first level, andthe duty-cycle control unit 128 shifts the first-level square wave pulseP₃ to a second level. Since the pulse enable signal P_(en) _(—) _(PWM)is also a square wave, the frequency (or cycle) of the PWM signalV_(PWM) is determined by the pulse enable signal P_(en) _(—) _(PWM).

For example, assuming that the first level is a high level and thesecond level is a low level, the square wave pulse generator 118receives the pulse enable signal P_(en) _(—) _(PWM) and rises the squarewave pulse P₃ to the high level, and the raised square wave pulse P₃ isshifted to the low level by a time constant determined by the duty-cyclecontrol unit 128. In this manner, a turn-on period of the square wavepulse P₃ is determined.

For example, an exemplary embodiment of the square wave pulse generator118 may be a 4528-series IC. As shown in FIG. 8, in a 4528-series IC,the RC pin of the square wave pulse generator 118 is connected to a nodeN₈₁ between the variable resistor R_(var) and the constant resistor R₈₃and the capacitor C₈₂, which are connected in series to each other. TheDC voltage V_(dc2) is applied across the variable resistor R_(var), theconstant resistor R₈₃ and the capacitor C₈₂. The pulse enable signalP_(en) _(—) _(PWM) is applied to the A pin of the square wave pulsegenerator 118.

The second amplifier 138 receives the output pulse P₃ of the square wavepulse generator 118 and outputs the PWM signal V_(PWM). The secondamplifier 138 receives the DC voltage V_(dc2) and may include a pair ofBJTs Q₈₁ and Q₈₂. The second amplifier 138 is similar to the firstamplifier 146 in the voltage converter 106 and a detailed descriptionthereof will thus be omitted. However, each of the transistors may havea different characteristic in the first amplifier 146 and the secondamplifier 138.

Referring again to FIG. 8, the square wave pulse generator 118 and thesecond amplifier 138 receive the DC voltage V_(dc2) from the voltageconverter 106, the square wave pulse generator 118 generates the squarewave pulse P₃ in response to the pulse enable signal P_(en) _(—) _(PWM)from the voltage converter 106, and the second amplifier 138 receivesthe square wave pulse P₃ and generates the PWM signal V_(PWM).

As described above, the duty cycle of the PWM signal V_(PWM) isdetermined by the duty-cycle control unit 128 which is a peripheralcircuit of the square wave pulse generator 118, and the turn-on time andfrequency of the PWM signal V_(PWM) are determined by the pulse enablesignal P_(en) _(—) _(PWM).

The output of the PWM controller 108, i.e., the PWM signal V_(PWM), maybe a square wave signal with a frequency ranging from 20 to 100 kHz orhigher, and the pulse width modulation may be controlled at a duty cycleranging from 1 to 100%.

In the duty-cycle control unit 128, the variable resistor R_(var) may bedirectly combined with an operating unit (not shown) for dimming the ACLED so that the resistance of the variable resistor R_(var) may beadjusted by the operating unit to adjust the duty cycle of the PWMsignal V_(PWM) to thereby dim the AC LED.

FIG. 9A, FIG. 9B, and FIG. 9C illustrate some PWM signals for dimmingthe AC LED. More specifically, FIG. 9A illustrates a waveform when a PWMsignal V_(PWM) has a duty cycle of 1%; FIG. 9B illustrates a waveformwhen a PWM signal V_(PWM) has a duty cycle of 70%; and FIG. 9Cillustrates a waveform when a PWM signal V_(PWM) has a duty cycle of100%.

Referring to FIG. 9A, the pulse enable signal P_(en) _(—) _(PWM) has apredetermined frequency and, as described above, has the PWM signalV_(PWM) enabled and determines a frequency of the PWM signal V_(PWM).

When the PWM signal V_(PWM) has a duty cycle of 1% by adjusting thevariable resistor R_(var) in FIG. 8, the waveform of the PWM signalV_(PWM) may be obtained as shown in FIG. 9A. In this case, since theperiod during which the switch 110 is turned on is very short, the ACLED produces a very low optical power.

Referring to FIG. 9B, the pulse enable signal P_(en) _(—) _(PWM) has thesame frequency as the pulse enable signal P_(en) _(—) _(PWM) in FIG. 9Aand the variable resistor R_(var) is adjusted so that the PWM signalV_(PWM) has a duty cycle of 70%. In this case, since the switch 110 isturned on longer than in FIG. 9A, the AC LED may produce an opticalpower greater than in FIG. 9A. Referring to FIG. 9C, the pulse enablesignal P_(en) _(—) _(PWM) has the same frequency as the pulse enablesignal P_(en) _(—) _(PWM) in FIG. 9A and the variable resistor R_(var)is adjusted so that the PWM signal V_(PWM) has a duty cycle of 100%. Inthis case, since the switch 110 is kept on, the AC LED may producemaximum optical power.

FIG. 10 is a circuit diagram of an embodiment of the switch 110 in FIG.3. When the PWM signal V_(PWM) is at a first level, the switch 110 is ina first operating mode during a positive half cycle of the AC voltagesource and is in a second operating mode during a negative half cycle ofthe AC voltage source. In this case, if the EMI filter 102 is positionedfollowing the AC voltage source (see reference numeral 120 in FIG. 3),electromagnetic interference is eliminated from the AC voltage source bythe EMI filter 102 and AC voltage having reduced electromagneticinterference (i.e., v_(out) in FIG. 5A or FIG. 5B) is then provided tothe switch 110.

For example, the first level and a second level of the PWM signalV_(PWM), respectively, indicate a voltage level to turn on thetransistors Q₁₀₁ and Q₁₀₂ and a voltage level between the gate andsource to turn off the transistors Q₁₀₁ and Q₁₀₂.

Since the AC voltage is applied to the switch 110 and the AC LED isused, two operating modes having two different current paths areemployed accordingly.

The switch 110 includes the first switching transistor Q₁₀₁ and thesecond switching transistor Q₁₀₂ and a first inverse diode Qd₁₀₁ and asecond inverse diode Qd₁₀₂ which are connected in parallel,respectively, to the first switching transistor Q₁₀₁ and the secondswitching transistor Q₁₀₂.

The first switching transistor Q₁₀₁ and the second switching transistorQ₁₀₂ are turned on or off by the PWM signal V_(PWM) and connected inseries to each other.

The first inverse diode Qd₁₀₁ is connected in parallel between the drainand source of the first switching transistor Q₁₀₁ and the second inversediode Qd₁₀₂ is connected in parallel between the drain and source of thesecond switching transistor Q₁₀₂.

In FIG. 10, in the first operating mode, current flows through the firstswitching transistor Q₁₀₁ and the second inverse diode Qd₁₀₂. In thesecond operating mode, current flows through the second switchingtransistor Q₁₀₂ and the first inverse diode Qd₁₀₁. That is, if the PWMsignal V_(PWM) is at a level to turn on the switching transistors Q₁₀₁and Q₁₀₂ (the first level in the example above), the switchingtransistors Q₁₀₁ and Q₁₀₂ are turned on and only a forward-biased diode(Qd₁₀₂ in the first operating mode; Qd₁₀₁ in the second operating mode)conducts current, resulting in different current paths.

Thus, in an exemplary embodiment of bidirectional switching according tothe AC voltage under control of the pulse width modulation signalV_(PWM) to drive the AC LED 180, the switch 110 may be in the firstoperating mode during the positive half cycle of the AC voltage sourceand in the second operating mode during the negative half cycle of theAC voltage source while the first level and the second level of the PWMsignal V_(PWM), respectively, indicate the voltage level to turn on thetransistors Q₁₀₁ and Q₁₀₂ and the voltage level to turn off thetransistors Q₁₀₁ and Q₁₀₂.

The respective operating modes will now be described in detail.

For the first operating mode which is a positive half cycle of the ACvoltage v₁, since the first inverse diode Qd₁₀₁ does not conductcurrent, current flows or does not flow between the drain N₁₀₁ and thesource N₁₀₂ of the first switching transistor Q₁₀₁ according to the PWMsignal V_(PWM). On the contrary, since the second inverse diode Qd₁₀₂ isforward biased, current flows through the second inverse diode Qd₁₀₂between the source N₁₀₂ and the drain N₁₀₃ of the second switchingtransistor Q₁₀₂. As a result, in the first operating mode, the firstswitching transistor Q₁₀₁ is controlled according to the PWM signalV_(PWM) to dim the AC LED accordingly.

For the second operating mode which is a negative half cycle of the ACvoltage v₁, since the second inverse diode Qd₁₀₂ does not conductcurrent, current flows or does not flow between the drain N₁₀₃ and thesource N₁₀₂ of the second switching transistor Q₁₀₂ according to the PWMsignal V_(PWM). On the contrary, since the first inverse diode Qd₁₀₁ isforward biased, current flows through the first inverse diode Qd₁₀₁between the source N₁₀₂ and the drain N₁₀₁ of the first switchingtransistor Q₁₀₁. As a result, in the second operating mode, the secondswitching transistor Q₁₀₂ is controlled according to the PWM signalV_(PWM) to dim the AC LED accordingly.

Although an N-type MOSFET is employed as the switching transistors Q₁₀₁and Q₁₀₂ in FIG. 10, a P-type MOSFET may be used as the switchingtransistors Q₁₀₁ and Q₁₀₂ or any type of switching transistor may beemployed which is rapidly switched by the PWM signal V_(PWM) to apply ACpower to the AC LED.

FIG. 11A, FIG. 11B, and FIG. 11C are waveforms illustrating the relationbetween input voltage and input current of an AC LED according to dutycycles of a PWM signal V_(PWM) in an AC LED dimmer according to anexemplary embodiment of the present invention.

FIG. 11A illustrates a PWM signal V_(PWM) with a duty cycle of 1%; FIG.11B illustrates a PWM signal V_(PWM) with a duty cycle of 70%; FIG. 11Cillustrates a PWM signal V_(PWM) with a duty cycle of 100%. Hence, FIG.11A, FIG. 11B, and FIG. 11C may be waveforms illustrating the relationbetween the input voltage and input current of the AC LED, whichcorrespond to FIG. 9A, FIG. 9B, and FIG. 9C, respectively. In FIG. 11A,FIG. 11B, and FIG. 1 IC, the x-axis indicates time and the y-axisindicates voltage or current.

In FIG. 11A and FIG. 11B, since an on or off period of the switch 110 isincluded within the cycle of the PWM signal V_(PWM) according to a dutycycle of the PWM signal V_(PWM), the input voltage and current of the ACLED are changed accordingly. Hence, an internal cycle in a period duringwhich the input voltage of the AC LED is changed according to the PWMsignal V_(PWM) and an internal cycle in a period during which the inputcurrent appears are the same as the cycle of the PWM signal V_(PWM).

In FIG. 11C, since the PWM signal V_(PWM) has a duty cycle of 100%, theswitch 110 is kept on, and, therefore, the voltage and current waveformsof the AC voltage source are obtained.

The optical power of the AC LED depends on the voltage multiplied by thecurrent. Hence, as shown in FIG. 11A, FIG. 11B, and FIG. 11C, anincreased duty cycle of the PWM signal V_(PWM) leads to an increasedpeak value; therefore, an increased duty cycle of the PWM signal V_(PWM)leads to an increased optical power of the AC LED.

The PWM signal V_(PWM) may be linearly controlled by adjusting the dutycycle to a predetermined value (between 1 and 100%).

As described above, the AC LED dimmer can achieve an efficient,wide-range dimming function using the PWM signal. Particularly, the ACLED dimmer can solve a limited dimming range and harmonics problems inthe conventional dimmer using the Triac.

An exemplary embodiment of an AC LED dimming method includes receivingAC voltage and generating a pulse width modulation signal; driving an ACLED under control of the pulse width modulation signal; and dimming theAC LED by adjusting a duty cycle of the pulse width modulation signal.

The PWM signal may be produced using a variety of ICs and peripheralcircuits. For example, as shown in FIG. 6, FIG. 7, FIG. 8 and FIG. 10,the above-mentioned exemplary embodiments of elements to produce the PWMsignal in the AC LED dimmer may be employed. Producing the PWM signal bymeans of the elements is described above and a detailed descriptionthereof will thus be omitted.

According to the AC LED dimming method, the AC LED is dimmed byadjusting the duty cycle of the PWM signal. The AC LED dimming methodmay further include eliminating electromagnetic interference included inthe AC voltage applied to produce the PWM signal or drive the AC LED.

For example, the electromagnetic interference may be eliminated by theexemplary embodiment of the EMI filter illustrated in FIG. 5A or FIG.5B.

Another exemplary embodiment of an AC LED dimming method includesreceiving and full-wave rectifying AC voltage; receiving the full-waverectified voltage, generating full-wave rectified stepped-up voltage,and generating a pulse enable signal; receiving the full-wave rectifiedstepped-up voltage and generating a pulse width modulation signal inresponse to the pulse enable signal; switching bidirectionally accordingto the AC voltage under control of the pulse width modulation signal todrive an AC LED; and dimming the AC LED by adjusting a duty cycle of thepulse width modulation signal.

The respective operations in the AC LED dimming method may be describedwith reference to FIG. 6, FIG. 7, FIG. 8 and FIG. 10, for example. Morespecifically, full-wave rectifying the AC voltage may be performed bythe rectifier 104 in FIG. 6; generating the full-wave rectifiedstepped-up voltage and the pulse enable signal may be performed by thevoltage converter 106 in FIG. 7; generating the pulse width modulationsignal may be performed by the controller 108 in FIG. 8; driving the ACLED by bidirectional switching may be performed by the switch 110 inFIG. 10.

Further, dimming the AC LED by adjusting the duty cycle may be achievedby the duty-cycle control unit 128 configured such that the variableresistor R_(var) is directly combined with the operating unit (notshown) for dimming the AC LED.

Similarly, the AC LED dimming method may further include eliminatingelectromagnetic interference included in the AC voltage applied toproduce the PWM signal or drive the AC LED.

The AC LED dimming method can achieve an efficient, wide-range dimmingfunction using the PWM control scheme. Further, the AC LED dimmer cansuppress harmonics.

As apparent from the above description, according to the exemplaryembodiments of the present invention, the AC LED dimmer and the dimmingmethod employ a pulse width modulation scheme capable of addressing theproblem of the conventional dimmer in which the dimming range is limitedby the drive voltage of the Triac and the characteristics of theresistor and capacitor of the R/C phase controller.

Further, according to the exemplary embodiments of the presentinvention, the AC LED dimmer and the dimming method thereof can solvethe problem of the conventional dimmer in which a number of harmonicsare produced in the turn-on switching operation.

In addition, according to the exemplary embodiments of the presentinvention, the AC LED dimmer and the dimming method can reduce orminimize flickering of the AC LED caused by the insufficient operatingmargin of the resistor and capacitor of the R/C phase controller in theconventional dimmer.

The various embodiments described above can be combined to providefurther embodiments. All patents, patent application publications,patent applications, foreign patents, foreign patent applications andnon-patent publications referred to in this specification and/or listedin the Application Data Sheet are incorporated herein by reference, intheir entirety. Aspects of the embodiments can be modified, if necessaryto employ concepts of the various patents, applications and publicationsto provide yet further embodiments.

These and other changes can be made to the embodiments in light of theabove-detailed description. It will be apparent to those skilled in theart that various modifications and variations can be made in the presentinvention without departing from the spirit or scope of the invention.In general, in the following claims, the terms used should not beconstrued to limit the claims to the specific embodiments disclosed inthe specification and the claims, but should be construed to include allpossible embodiments along with the full scope of equivalents to whichsuch claims are entitled. Accordingly, the claims are not limited by thedisclosure. Thus, it is intended that the present invention cover themodifications and variations of this invention provided they come withinthe scope of the appended claims and their equivalents.

1. An alternating current (AC) light-emitting diode (LED) dimmer,comprising: a rectifier to full-wave rectify a voltage from an ACvoltage power source to generate a first full-wave rectified voltage; avoltage converter to generate a second full-wave rectified isolatedvoltage from the first full-wave rectified voltage, and to generate apulse enable signal; a pulse width modulation controller to be suppliedwith the second full-wave rectified isolated voltage and to generate apulse width modulation signal with the frequency of the pulse enablesignal and with an adjustable duty-cycle ratio to dim an AC LED; and aswitch to be controlled by the pulse width modulation signal to drivethe AC LED by selectively providing the AC voltage to the AC LED.
 2. TheAC LED dimmer according to claim 1, further comprising: anelectromagnetic interference (EMI) filter connected between the ACvoltage source and the switch to reduce electromagnetic interferencefrom the AC voltage source.
 3. The AC LED dimmer according to claim 2,wherein the EMI filter is a line filter comprising a filter capacitorand a common mode inductor.
 4. The AC LED dimmer according to claim 3,wherein the common mode inductor comprises at least two stages connectedto each other in series.
 5. The AC LED dimmer according to claim 1,wherein the rectifier comprises: a voltage divider to divide voltage ofthe AC voltage source; a first full-wave rectifying unit to firstfull-wave rectify the divided voltage; and a voltage stabilizer tostabilize the voltage first full-wave rectified by the first full-waverectifying unit.
 6. The AC LED dimmer according to claim 5, wherein thevoltage stabilizer comprises a capacitor connected between an output ofthe rectifier and a ground.
 7. The AC LED dimmer according to claim 5,wherein the voltage divider comprises a capacitor connected to the ACvoltage source and a resistor connected in series to the capacitor, thefirst full-wave rectifying unit being connected between the resistor andthe AC voltage source.
 8. The AC LED dimmer according to claim 7,wherein the voltage divider further comprises a pair of Zener diodesconnected in parallel to an input of the first full-wave rectifying unitto supply a Zener voltage.
 9. The AC LED dimmer according to claim 1,wherein the voltage converter comprises: a pulse generator to receive anoutput voltage of the rectifier and to generate a pulse signal; anamplifier to receive the pulse signal and to generate a square-wavesignal; a transformer to receive the square-wave signal in its primarywinding and to induce a stepped-up voltage in its secondary winding; asecond full-wave rectifying unit to second full-wave rectify thestepped-up voltage in the secondary winding and output the pulse enablesignal to be applied to the pulse width modulation controller; and avoltage stabilizer to stabilize the voltage second full-wave rectifiedby the second full-wave rectifying unit.
 10. The AC LED dimmer accordingto claim 9, further comprising a noise filter connected between a groundat the primary winding of the transformer and a ground at an output ofthe voltage converter.
 11. The AC LED dimmer according to claim 9,further comprising a DC cutoff capacitor connected in series between anoutput of the first amplifier and the primary winding of thetransformer.
 12. The AC LED dimmer according to claim 1, wherein thepulse width modulation controller comprises: a duty cycle controlcircuit to control a duty cycle of a square-wave pulse; a square-wavepulse generator to receive the pulse enable signal, to shift thesquare-wave pulse to a first level, and to shift the square-wave pulseto a second level in response to control of the duty cycle controlcircuit; and an amplifier to receive an output of the square-wave pulsegenerator and to output the pulse width modulation signal.
 13. The ACLED dimmer according to claim 1, wherein when the pulse width modulationsignal is at a first level, the switch has a first operating mode duringa positive half cycle of the AC voltage source and a second operatingmode during a negative half cycle of the AC voltage source.
 14. The ACLED dimmer according to claim 1, wherein the switch is a bidirectionalswitch.
 15. An alternating current (AC) light-emitting diode (LED)dimming method, comprising: first full-wave rectifying a voltage from anAC voltage power source to generate a first full-wave rectified voltage;generating from the first full-wave rectified voltage a second full-waverectified isolated voltage and a pulse enable signal; generating a pulsewidth modulation signal with the frequency of the pulse enable signaland with an adjustable duty-cycle ratio to dim an AC LED, wherein thesecond full-wave rectified isolated voltage is used to generate a pulsewidth modulation signal; and driving the AC LED by selectively providingthe AC voltage to the AC LED according to the pulse width modulationsignal.
 16. The AC LED dimming method according to claim 15, furthercomprising: dimming the AC LED by adjusting a duty cycle of the pulsewidth modulation signal.
 17. The AC LED dimming method according toclaim 15, further comprising: reducing electromagnetic interferenceassociated with the AC voltage.